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| Final Electrical Specifications LT6600-2.5 Very Low Noise, Differential Amplifier and 2.5MHz Lowpass Filter June 2003 FEATURES s s s s DESCRIPTIO s s s s s Programmable Differential Gain via Two External Resistors Adjustable Output Common Mode Voltage Operates and Specified with 3V, 5V, 5V Supplies 0.5dB Ripple 4th Order Lowpass Filter with 2.5MHz Cutoff 86dB S/N with 3V Supply and 1VRMS Output Low Distortion, 1VRMS, 800 Load 1MHz: 95dBc 2nd, 88dBc 3rd Fully Differential Inputs and Outputs Compatible with Popular Differential Amplifier Pinouts SO-8 Package The LT(R)6600-2.5 combines a fully differential amplifier with a 4th order 2.5MHz lowpass filter approximating a Chebyshev frequency response. Most differential amplifiers require many precision external components to tailor gain and bandwidth. In contrast, with the LT6600-2.5, two external resistors program differential gain, and the filter's 2.5MHz cutoff frequency and passband ripple are internally set. The LT6600-2.5 also provides the necessary level shifting to set its output common mode voltage to accommodate the reference voltage requirements of A/Ds. Using a proprietary internal architecture, the LT6600-2.5 integrates an antialiasing filter and a differential amplifier/ driver without compromising distortion or low noise performance. At unity gain the measured in band signal-to-noise ratio is an impressive 86dB. At higher gains the input referred noise decreases so the part can process smaller input differential signals without significantly degrading the output signal-to-noise ratio. The LT6600-2.5 also features low voltage operation. The differential design provides outstanding performance for a 4VP-P signal level while the part operates with a single 3V supply. The LT6600-2.5 is available in an SO-8 package. For similar devices with higher cutoff frequency, refer to the LT6600-10 and LT6600-20 data sheets. APPLICATIO S s s s s High Speed ADC Antialiasing and DAC Smoothing in Networking or Cellular Base Station Applications High Speed Test and Measurement Equipment Medical Imaging Drop-in Replacement for Differential Amplifiers , LTC and LT are registered trademarks of Linear Technology Corporation. TYPICAL APPLICATIO 5V 12 0 0.1F 1580 -12 -24 7 0.01F VIN+ 1580 8 - GAIN (dB) VIN- 1 3 4 VOUT+ VOUT - -36 -48 -60 -72 2 LT6600-2.5 + 6 5 660025 TA01a -84 -96 100k 1M 10M FREQUENCY (Hz) 50M 660025 TA01b Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. U Amplitude Response VS = 2.5V U U 660025i 1 LT6600-2.5 ABSOLUTE (Note 1) AXI U RATI GS PACKAGE/ORDER I FOR ATIO TOP VIEW IN - 1 VOCM 2 V+ 3 OUT + 4 8 7 6 5 IN + VMID V- OUT - Total Supply Voltage ................................................ 11V Operating Temperature Range (Note 6) ...-40C to 85C Specified Temperature Range (Note 7) ....-40C to 85C Junction Temperature ........................................... 150C Storage Temperature Range ................. - 65C to 150C Lead Temperature (Soldering, 10 sec).................. 300C ORDER PART NUMBER LT6600CS8-2.5 LT6600IS8-2.5 S8 PART MARKING 660025 600I25 S8 PACKAGE 8-LEAD PLASTIC SO TJMAX = 150C, JA = 100C/W Consult LTC Marketing for parts specified with wider operating temperature ranges. The q denotes specifications that apply over the full operating temperature range, otherwise specifications are at TA = 25C. Unless otherwise specified VS = 5V (V+ = 5V, V - = 0V), RIN = 1580, and RLOAD = 1k. PARAMETER Filter Gain, VS = 3V RIN = 1580 CONDITIONS VIN = 2VP-P, fIN = DC to 260kHz VIN = 2VP-P, fIN = 700kHz (Gain Relative to 260kHz) VIN = 2VP-P, fIN = 1.9MHz (Gain Relative to 260kHz) VIN = 2VP-P, fIN = 2.2MHz (Gain Relative to 260kHz) VIN = 2VP-P, fIN = 2.5MHz (Gain Relative to 260kHz) VIN = 2VP-P, fIN = 7.5MHz (Gain Relative to 260kHz) VIN = 2VP-P, fIN = 12.5MHz (Gain Relative to 260kHz) VIN = 2VP-P, fIN = DC to 260kHz VIN = 2VP-P, fIN = 700kHz (Gain Relative to 260kHz) VIN = 2VP-P, fIN = 1.9MHz (Gain Relative to 260kHz) VIN = 2VP-P, fIN = 2.2MHz (Gain Relative to 260kHz) VIN = 2VP-P, fIN = 2.5MHz (Gain Relative to 260kHz) VIN = 2VP-P, fIN = 7.5MHz (Gain Relative to 260kHz) VIN = 2VP-P, fIN = 12.5MHz (Gain Relative to 260kHz) VIN = 2VP-P, fIN = DC to 260kHz VIN = 2VP-P, fIN = DC to 260kHz, VS = 3V VIN = 2VP-P, fIN = DC to 260kHz, VS = 5V VIN = 2VP-P, fIN = DC to 260kHz, VS = 5V fIN = 260kHz, VIN = 2VP-P Noise BW = 10kHz to 2.5MHz 1MHz, 1VRMS, RL = 800 2nd Harmonic 3rd Harmonic Measured Between Pins 4 and 5 VS = 5V VS = 3V Average of Pin 1 and Pin 8 MIN - 0.5 - 0.15 - 0.2 - 0.6 - 2.1 TYP 0.1 0 0.2 0.1 0.9 - 34 - 51 -0.1 0 0.2 0.1 -0.9 - 34 - 51 - 0.1 11.8 11.8 11.7 780 51 95 88 9.3 5.5 - 15 MAX 0.4 0.1 0.6 0.5 0 - 31 0.4 0.1 0.6 0.5 0 -31 0.4 12.3 12.3 12.2 UNITS dB dB dB dB dB dB dB dB dB dB dB dB dB dB dB dB dB dB ppm/C VRMS dBc dBc VP-P DIFF VP-P DIFF A ELECTRICAL CHARACTERISTICS q q q q q q q q q q q q Filter Gain, VS = 5V RIN = 1580 - 0.5 - 0.15 - 0.2 - 0.6 - 2.1 Filter Gain, VS = 5V Filter Gain, RIN = 402 - 0.6 11.3 11.3 11.2 Filter Gain Temperature Coefficient (Note 2) Noise Distortion (Note 4) Differential Output Swing Input Bias Current q q q 8.8 5.1 - 35 660025i 2 U W U U WW W LT6600-2.5 The q denotes specifications that apply over the full operating temperature range, otherwise specifications are at TA = 25C. Unless otherwise specified VS = 5V (V+ = 5V, V - = 0V), RIN = 1580, and RLOAD = 1k. PARAMETER Input Referred Differential Offset CONDITIONS RIN = 1580 MIN VS = 3V VS = 5V VS = 5V VS = 3V VS = 5V VS = 5V VS = 3V VS = 5V VS = 5V VS = 3V VS = 5V VS = 5V VS = 3V VS = 5V VS = 5V VS = 5V VS = 3V VOCM = VMID= VS/2 VS = 5V VS = 3V VS = 3V, VS = 5V VS = 3V, VS = 5V VS = 5V q q q q q q q q q q q q q q q q q q q q q ELECTRICAL CHARACTERISTICS RIN = 402 Differential Offset Drift Input Common Mode Voltage (Note 3) TYP 5 5 5 3 3 3 10 MAX 25 30 35 13 16 20 1.5 3.0 1.0 1.5 3.0 2.0 45 45 35 2.55 7.7 Differential Input = 500mVP-P, RIN = 402 Differential Input = 2VP-P, Pin 7 at Mid-Supply Output Common Mode Voltage (Note 5) Output Common Mode Offset (with Respect to Pin 2) Common Mode Rejection Ratio Voltage at VMID (Pin 7) VMID Input Resistance VOCM Bias Current Power Supply Current 0.0 0.0 -2.5 1.0 1.5 -1.0 -25 -30 -55 2.46 4.3 -15 -10 10 5 -10 63 2.51 1.5 5.7 -3 -3 26 28 30 33 36 UNITS mV mV mV mV mV mV V/C V V V V V V mV mV mV dB V V k A A mA mA mA Note 1: Absolute Maximum Ratings are those values beyond which the life of a device may be impaired. Note 2: This is the temperature coefficient of the internal feedback resistors assuming a temperature independent external resistor (RIN). Note 3: The input common mode voltage is the average of the voltages applied to the external resistors (RIN). Specification guaranteed for RIN 402. Note 4: Distortion is measured differentially using a single-ended stimulus. The input common mode voltage, the voltage at Pin 2, and the voltage at Pin 7 are equal to one half of the total power supply voltage. Note 5: Output common mode voltage is the average of the voltages at Pins 4 and 5. The output common mode voltage is equal to the voltage applied to Pin 2. Note 6: Both the LT6600CS8-2.5 and LT6600IS8-2.5 are guaranteed functional over the operating temperature range of -40C to 85C. Note 7: The LT6600CS8-2.5 is guaranteed to meet specified performance from 0C to 70C and is designed, characterized and expected to meet specified performance from -40C and 85C, but is not tested or QA sampled at these temperatures. The LT6600IS8-2.5 is guaranteed to meet specified performance from -40C to 85C. 660025i 3 LT6600-2.5 PI FU CTIO S IN - and IN + (Pins 1, 8): Input Pins. Signals can be applied to either or both input pins through identical external resistors, RIN. The DC gain from differential inputs to the differential outputs is 1580/RIN. VOCM (Pin 2): Is the DC Common Mode Reference Voltage for the 2nd Filter Stage. Its value programs the common mode voltage of the differential output of the filter. Pin 2 is a high impedance input, which can be driven from an external voltage reference, or Pin 2 can be tied to Pin 7 on the PC board. Pin 2 should be bypassed with a 0.01F ceramic capacitor unless it is connected to a ground plane. V+ and V - (Pins 3, 6): Power Supply Pins. For a single 3.3V or 5V supply (Pin 6 grounded) a quality 0.1F ceramic bypass capacitor is required from the positive supply pin (Pin 3) to the negative supply pin (Pin 6). The bypass should be as close as possible to the IC. For dual supply applications, bypass Pin 3 to ground and Pin 6 to ground with a quality 0.1F ceramic capacitor. OUT+ and OUT - (Pins 4, 5): Output Pins. Pins 4 and 5 are the filter differential outputs. Each pin can drive a 100 and/or 50pF load to AC ground. VMID (Pin 7): The VMID pin is internally biased at midsupply, see block diagram. For single supply operation, the VMID pin should be bypassed with a quality 0.01F ceramic capacitor to Pin 6. For dual supply operation, Pin 7 can be bypassed or connected to a high quality DC ground. A ground plane should be used. A poor ground will increase noise and distortion. Pin 7 sets the output common mode voltage of the 1st stage of the filter. It has a 5.5k impedance, and it can be overridden with an external low impedance voltage source. 4 U U U 660025i LT6600-2.5 BLOCK DIAGRA VIN+ VIN- W RIN 8 IN + VMID 7 V+ 11k 1580 11k 800 V- OP AMP V- 6 OUT - 5 PROPRIETARY LOWPASS FILTER STAGE + VOCM 800 - + 800 +- VOCM - -+ 800 1580 1 RIN IN - 2 VOCM 3 V+ 4 660025 BD OUT + 660025i 5 LT6600-2.5 APPLICATIO S I FOR ATIO Interfacing to the LT6600-2.5 The LT6600-2.5 requires two equal external resistors, RIN, to set the differential gain to 1580/RIN. The inputs to the filter are the voltages VIN+ and VIN- presented to these external components, Figure 1. The difference between VIN+ and VIN- is the differential input voltage. The average of VIN+ and VIN- is the common mode input voltage. Similarly, the voltages VOUT+ and VOUT- appearing at Pins 4 and 5 of the LT6600-2.5 are the filter outputs. The difference between VOUT+ and VOUT- is the differential output voltage. The average of VOUT+ and VOUT- is the common mode output voltage. Figure 1 illustrates the LT6600-2.5 operating with a single 3.3V supply and unity passband gain; the input signal is DC coupled. The common mode input voltage is 0.5V, and the differential input voltage is 2VP-P. The common mode V 3 2 1 0 VIN+ + VIN VIN - 1580 VIN- t 1580 V 0.1F 2 1 0 -1 VIN+ 0.1F t VIN + V 3 2 1 0 500mVP-P (DIFF) VIN+ VIN- t 0.01F VIN + VIN - 6 U output voltage is 1.65V, and the differential output voltage is 2VP-P for frequencies below 2.5MHz. The common mode output voltage is determined by the voltage at pin 2. Since pin 2 is shorted to pin 7, the output common mode is the mid-supply voltage. In addition, the common mode input voltage can be equal to the mid-supply voltage of Pin 7. Figure 2 shows how to AC couple signals into the LT6600-2.5. In this instance, the input is a single-ended signal. AC coupling allows the processing of single-ended or differential signals with arbitrary common mode levels. The 0.1F coupling capacitor and the 1580 gain setting resistor form a high pass filter, attenuating signals below 1kHz. Larger values of coupling capacitors will proportionally reduce this highpass 3dB frequency. 3.3V 0.1F 1 7 0.01F 2 8 3 V 3 W UU - LT6600-2.5 + 4 VOUT+ VOUT- 2 1 0 VOUT+ VOUT- t 660025 F01 + 6 -5 Figure 1 3.3V 0.1F 1580 1 7 0.01F 1580 2 8 3 V 3 VOUT+ VOUT- 2 1 0 VOUT+ VOUT- - LT6600-2.5 + 4 + 6 - 5 660025 F02 Figure 2 5V 0.1F 402 1 7 2 8 3 V 3 VOUT+ 2 VOUT- 1 0 VOUT- VOUT+ - LT6600-2.5 + 4 + 6 - 5 402 + - 2V t 660025 F03 Figure 3 660025i LT6600-2.5 APPLICATIO S I FOR ATIO In Figure 3 the LT6600-2.5 is providing 12dB of gain. The common mode output voltage is set to 2V. Use Figure 4 to determine the interface between the LT6600-2.5 and a current output DAC. The gain, or "transimpedance," is defined as A = VOUT/IIN. To compute the transimpedance, use the following equation: A= 1580 * R1 ( ) (R1+ R2) By setting R1 + R2 = 1580, the gain equation reduces to A = R1(). The voltage at the pins of the DAC is determined by R1, R2, the voltage on Pin 7 and the DAC output current. Consider Figure 4 with R1 = 49.9 and R2 = 1540. The voltage at Pin 7 is 1.65V. The voltage at the DAC pins is given by: R1 R1 * R2 VDAC = VPIN7 * + IIN * R1 + R2 + 1580 R1 + R2 = 26mV + IIN * 48.3 IIN is IIN+ or IIN-. The transimpedance in this example is 49.6. Evaluating the LT6600-2.5 The low impedance levels and high frequency operation of the LT6600-2.5 require some attention to the matching networks between the LT6600-2.5 and other devices. The previous examples assume an ideal (0) source impedance and a large (1k) load resistance. Among practical examples where impedance must be considered is the evaluation of the LT6600-2.5 with a network analyzer. CURRENT OUTPUT DAC IIN- R1 IIN+ R1 R2 0.01F R2 1 7 8 3.3V 0.1F 3 -+ + 6 4 VOUT+ VOUT- 2 LT6600-2.5 - 5 660025 F04 Figure 4 U Figure 5 is a laboratory setup that can be used to characterize the LT6600-2.5 using single-ended instruments with 50 source impedance and 50 input impedance. For a 12dB gain configuration the LT6600-2.5 requires a 402 source resistance yet the network analyzer output is calibrated for a 50 load resistance. The 1:1 transformer, 53.6 and 388 resistors satisfy the two constraints above. The transformer converts the single-ended source into a differential stimulus. Similarly, the output of the LT6600-2.5 will have lower distortion with larger load resistance yet the analyzer input is typically 50. The 4:1 turns (16:1 impedance) transformer and the two 402 resistors of Figure 5, present the output of the LT6600-2.5 with a 1600 differential load, or the equivalent of 800 to ground at each output. The impedance seen by the network analyzer input is still 50, reducing reflections in the cabling between the transformer and analyzer input. Differential and Common Mode Voltage Ranges The rail-to-rail output stage of the LT6600-2.5 can process large differential signal levels. On a 3V supply, the output signal can be 5.1VP-P. Similarly, a 5V supply can support signals as large as 8.8VP-P. To prevent excessive power dissipation in the internal circuitry, the user must limit differential signal levels to 9VP-P. The two amplifiers inside the LT6600-2.5 have independent control of their output common mode voltage (see the "Block Diagram" section). The following guidelines will optimize the performance of the filter. Pin 7 can be allowed to float; Pin 7 must be bypassed to an AC ground with a 0.01F capacitor or some instability may be observed. Pin 7 can be driven from a low impedance 2.5V 0.1F NETWORK ANALYZER SOURCE 50 53.6 COILCRAFT TTWB-1010 1:1 388 1 7 2 8 388 COILCRAFT TTWB-16A 4:1 402 NETWORK ANALYZER INPUT 3 W U U - + - 6 4 LT6600-2.5 50 402 660025 F05 + 5 0.1F - 2.5V Figure 5 660025i 7 LT6600-2.5 APPLICATIO S I FOR ATIO source, provided it remains at least 1.5V above V - and at least 1.5V below V +. An internal resistor divider sets the voltage of Pin 7. While the internal 11k resistors are well matched, their absolute value can vary by 20%. This should be taken into consideration when connecting an external resistor network to alter the voltage of Pin 7. Pin 2 can be shorted to Pin 7 for simplicity. If a different common mode output voltage is required, connect Pin 2 to a voltage source or resistor network. For 3V and 3.3V supplies the voltage at Pin 2 must be less than or equal to the mid supply level. For example, voltage (Pin 2) 1.65V on a single 3.3V supply. For power supply voltages higher than 3.3V the voltage at Pin 2 can be set above mid supply. The voltage on Pin 2 should not exceed 1V below the voltage on Pin 7. The voltage on Pin 2 should not be more than 2V above the voltage on Pin 7. Pin 2 is a high impedance input. The LT6600-2.5 was designed to process a variety of input signals including signals centered around the mid-supply voltage and signals that swing between ground and a positive voltage in a single supply system (Figure 1). The range of allowable input common mode voltage (the average of VIN+ and VIN- in Figure 1) is determined by the power supply level and gain setting (see "Electrical Characteristics"). Common Mode DC Currents In applications like Figure 1 and Figure 3 where the LT6600-2.5 not only provides lowpass filtering but also level shifts the common mode voltage of the input signal, DC currents will be generated through the DC path between input and output terminals. Minimize these currents to decrease power dissipation and distortion. Consider the application in Figure 3. Pin 7 sets the output common mode voltage of the 1st differential amplifier inside the LT6600-2.5 (see the "Block Diagram" section) at 2.5V. Since the input common mode voltage is near 0V, there will be approximately a total of 2.5V drop across the series combination of the internal 1580 feedback resistor and the external 402 input resistor. The resulting 1.25mA common mode DC current in each input path, must be absorbed by the sources VIN+ and VIN-. Pin 2 sets the common mode output voltage of the 2nd differential 8 U amplifier inside the LT6600-2.5, and therefore sets the common mode output voltage of the filter. Since, in the example of Figure 3, Pin 2 differs from Pin 7 by 0.5V, an additional 625A (312A per side) of DC current will flow in the resistors coupling the 1st differential amplifier output stage to filter output. Thus, a total of 3.125mA is used to translate the common mode voltages. A simple modification to Figure 3 will reduce the DC common mode currents by 36%. If Pin 7 is shorted to Pin 2 the common mode output voltage of both op amp stages will be 2V and the resulting DC current will be 2mA. Of course, by AC coupling the inputs of Figure 3, the common mode DC current can be reduced to 625A. Noise The noise performance of the LT6600-2.5 can be evaluated with the circuit of Figure 6. Given the low noise output of the LT6600-2.5 and the 6dB attenuation of the transformer coupling network, it will be necessary to measure the noise floor of the spectrum analyzer and subtract the instrument noise from the filter noise measurement. Example: With the IC removed and the 25 resistors grounded, Figure 6, measure the total integrated noise (eS) of the spectrum analyzer from 10kHz to 2.5MHz. With the IC inserted, the signal source (VIN) disconnected, and the input resistors grounded, measure the total integrated noise out of the filter (eO). With the signal source connected, set the frequency to 100kHz and adjust the amplitude until VIN measures 100mVP-P. Measure the output amplitude, VOUT, and compute the passband gain 2.5V 0.1F VIN RIN 3 COILCRAFT TTWB-1010 25 1:1 SPECTRUM ANALYZER INPUT 1 7 2 8 RIN W U U -+ + 6 4 LT6600-2.5 50 25 66002 F06 - 5 0.1F - 2.5V Figure 6 660025i LT6600-2.5 APPLICATIO S I FOR ATIO NOISE SPECTRAL DENSITY (nVRMS/Hz) A = VOUT/VIN. Now compute the input referred integrated noise (eIN) as: eIN = (eO )2 - (eS )2 A Table 1 lists the typical input referred integrated noise for various values of RIN. Figure 7 is plot of the noise spectral density as a function of frequency for an LT6600-2.5 with RIN = 1580 using the fixture of Figure 6 (the instrument noise has been subtracted from the results). Table 1. Noise Performance PASSBAND GAIN (V/V) 4 2 1 INPUT REFERRED INTEGRATED NOISE 10kHz TO 2.5MHz 18VRMS 29VRMS 51VRMS INPUT REFERRED INTEGRATED NOISE 10kHz TO 5MHz 23VRMS 39VRMS 73VRMS RIN 402 806 1580 The noise at each output is comprised of a differential component and a common mode component. Using a transformer or combiner to convert the differential outputs to single-ended signal rejects the common mode noise and gives a true measure of the S/N achievable in the system. Conversely, if each output is measured individually and the noise power added together, the resulting calculated noise level will be higher than the true differential noise. Power Dissipation The LT6600-2.5 amplifiers combine high speed with largesignal currents in a small package. There is a need to ensure that the dies's junction temperature does not exceed 150C. The LT6600-2.5 package has Pin 6 fused to the lead frame to enhance thermal conduction when connecting to a ground plane or a large metal trace. Metal trace and plated through-holes can be used to spread the heat generated by the device to the backside of the PC board. For example, on a 3/32" FR-4 board with 2oz copper, a total of 660 square millimeters connected to Pin 6 of the LT6600-2.5 (330 square millimeters on each side of the PC board) will result in a thermal resistance, JA, of U 50 100 40 SPECTRAL DENSITY 30 60 80 W U U INTEGRATED NOISE (VRMS) 20 40 10 INTEGRATED 0 0.01 20 0 0.1 1 10 66002 F07 FREQUENCY (MHz) Figure 7. Input Referred Noise, Gain = 1 Table 2. LT6600-2.5 SO-8 Package Thermal Resistance COPPER AREA TOPSIDE (mm2) 1100 330 35 35 0 BACKSIDE (mm2) 1100 330 35 0 0 BOARD AREA (mm2) 2500 2500 2500 2500 2500 THERMAL RESISTANCE (JUNCTION-TO-AMBIENT) 65C/W 85C/W 95C/W 100C/W 105C/W about 85C/W. Without extra metal trace connected to the V - pin to provide a heat sink, the thermal resistance will be around 105C/W. Table 2 can be used as a guide when considering thermal resistance. Junction temperature, TJ, is calculated from the ambient temperature, TA, and power dissipation, PD. The power dissipation is the product of supply voltage, VS, and supply current, IS. Therefore, the junction temperature is given by: TJ = TA + (PD * JA) = TA + (VS * IS * JA) where the supply current, IS, is a function of signal level, load impedance, temperature and common mode voltages. For a given supply voltage, the worst-case power dissipation occurs when the differential input signal is maximum, the common mode currents are maximum (see Applications Information regarding Common Mode DC 660025i 9 LT6600-2.5 APPLICATIO S I FOR ATIO Currents), the load impedance is small and the ambient temperature is maximum. To compute the junction temperature, measure the supply current under these worstcase conditions, estimate the thermal resistance from Table 2, then apply the equation for TJ. For example, using the circuit in Figure 3 with DC differential input voltage of 1V, a differential output voltage of 4V, no load resistance and an ambient temperature of 85C, the supply current 10 U (current into Pin 3) measures 37.6mA. Assuming a PC board layout with a 35mm2 copper trace, the JA is 100C/W. The resulting junction temperature is: TJ = TA + (PD * JA) = 85 + (5 * 0.0376 * 100) = 104C When using higher supply voltages or when driving small impedances, more copper may be necessary to keep TJ below 150C. 660025i W U U LT6600-2.5 PACKAGE DESCRIPTIO .050 BSC 8 .245 MIN .030 .005 TYP RECOMMENDED SOLDER PAD LAYOUT .010 - .020 x 45 (0.254 - 0.508) .008 - .010 (0.203 - 0.254) 0- 8 TYP .016 - .050 (0.406 - 1.270) NOTE: 1. DIMENSIONS IN INCHES (MILLIMETERS) 2. DRAWING NOT TO SCALE 3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm) U S8 Package 8-Lead Plastic Small Outline (Narrow .150 Inch) (Reference LTC DWG # 05-08-1610) .189 - .197 (4.801 - 5.004) NOTE 3 7 6 5 .045 .005 .160 .005 .228 - .244 (5.791 - 6.197) .150 - .157 (3.810 - 3.988) NOTE 3 1 2 3 4 .053 - .069 (1.346 - 1.752) .004 - .010 (0.101 - 0.254) .014 - .019 (0.355 - 0.483) TYP .050 (1.270) BSC SO8 0303 660025i 11 LT6600-2.5 RELATED PARTS PART NUMBER LTC 1565-31 LTC1566-1 LT1567 LT1568 LT6600-10 LT6600-20 (R) DESCRIPTION 650kHz Linear Phase Lowpass Filter Low Noise, 2.3MHz Lowpass Filter Very Low Noise, High Frequency Filter Building Block Very Low Noise, 4th Order Building Block Very Low Noise Differential Amplifier and 10MHz Lowpass Filter Very Low Noise Differential Amplifier and 20MHz Lowpass Filter COMMENTS Continuous Time, SO8 Package, Fully Differential Continuous Time, SO8 Package 1.4nV/Hz Op Amp, MSOP Package, Fully Differential Lowpass and Bandpass Filter Designs Up to 10MHz, Differential Outputs 82dB S/N with 3V Supply, SO-8 Package 76dB S/N with 3V Supply, SO-8 Package 660025i 12 Linear Technology Corporation 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 q LT/TP 0603 1K * PRINTED IN USA FAX: (408) 434-0507 q www.linear.com (c) LINEAR TECHNOLOGY CORPORATION 2003 |
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